systemverilog

name	systemverilog
description	SystemVerilog coding convention and design guideline skill. Enforces lowRISC style + project overrides for all .sv/.v file generation. Covers naming, module structure, power optimization, FPGA considerations, and pipelining for timing closure.
user-invocable	false

SystemVerilog coding standards and design guidelines. All agents generating or modifying .sv, .v files must follow the rules in this skill.

Target standard: IEEE 1800-2009 for synthesizable RTL.

• 2009 features: always_ff, always_comb, logic, typedef enum/struct, packages — all available
• interface/modport is 2009 standard but iverilog unsupported — do NOT generate in RTL (see §4.3)
• 2012+ features (checker, interface class, let, soft constraint) are verification-only — do NOT use in RTL
• Tool flags: iverilog uses -g2012 for parser compatibility (2012 parser handles 2009 code)

Baseline: lowRISC SystemVerilog Coding Style Guide (https://github.com/lowRISC/style-guides/blob/master/VerilogCodingStyle.md) Project overrides take precedence over default lowRISC rules.

<Use_When>

• When writing or modifying .sv, .svh, .v, .vh files
• During Phase 4 (RTL implementation) work
• During Phase 5 (Verification) when writing SVA or SV testbenches
• When preparing code before running rtl-lint-check or rtl-synth-check skills
• Agents: rtl-coder, sva-extractor, testbench-dev, lint-checker </Use_When>

<Do_Not_Use_When>

• When writing SystemC/C++ code → use systemc skill
• When writing Python cocotb tests → refer to cocotb rules in rtl-p5s-func-verify skill
• When only writing documentation </Do_Not_Use_When>

<Why_This_Exists> Consistent coding standards ensure lint pass rate, synthesis quality, and team readability all at once. Although based on lowRISC, this project has its own overrides for port naming, clock/reset rules, etc., so they are managed as a separate skill to ensure all SV-generating agents reference the same rules. </Why_This_Exists>

<Execution_Policy>

• The rules in this skill apply to all agents that generate SV code
• Violations will result in a FAIL verdict from the rtl-lint-check skill
• Use templates/module-template.sv as the starting point for new modules
• Review examples/good-vs-bad.sv for correct/incorrect pattern examples
• See references/coding-style-guide.md for detailed project overrides vs. original lowRISC rules </Execution_Policy>

1. Project Overrides (Take Precedence Over lowRISC)

IMPORTANT — The following 3 rules differ from the lowRISC guide and must always be applied.

1.1 Port Direction Prefix (Mandatory, Clock/Reset Excepted)

• Input: i_, Output: o_, Bidirectional: io_ — mandatory
• Example: i_data, o_valid, io_sda (NOT data_i, valid_o)
• Exception: Clock and reset ports do not need the i_ prefix (clk, sys_clk, rst_n, sys_rst_n)
• Using suffixes (_i, _o, _io) is forbidden
• lowRISC uses suffixes, but this project requires prefixes (clock/reset excepted)

1.2 Clock Naming

• Single clock: clk (default) or {domain}_clk (multi-clock)
• Multi-clock domains: sys_clk, pixel_clk, axi_clk
• NOT clk_i, NOT suffix

1.3 Reset Naming

• Single reset: rst_n (default) or {domain}_rst_n (multi-domain)
• Active-low asynchronous reset is mandatory
• Example: rst_n, sys_rst_n, pixel_rst_n (NOT rst_ni)

1.4 CamelCase Prohibition (Additional Override)

• lowRISC uses UpperCamelCase for Parameters and Enum values
• This project prohibits CamelCase entirely
• Parameter: ALL_CAPS (DATA_WIDTH, NOT DataWidth)
• Localparam (internal): L_ prefix + ALL_CAPS (L_ADDR_BITS, NOT AddrBits)
• Enum values: ALL_CAPS (ST_IDLE, NOT StIdle)

2. Naming Conventions

IMPORTANT — CamelCase is completely prohibited. All identifiers must use only snake_case or ALL_CAPS. Detailed rules: see references/coding-style-guide.md.

Target	Rule	Example
Module	snake_case	axi_lite_slave
Parameter (externally configurable)	ALL_CAPS	DATA_WIDTH, DEPTH
Local parameter (internal only)	L_ prefix + ALL_CAPS	L_ADDR_BITS, L_CNT_MAX
Type (typedef)	snake_case_t suffix	state_t, bus_req_t
Enum type (typedef enum)	snake_case_e suffix	state_e, cmd_type_e
Enum values	ALL_CAPS	ST_IDLE, WAIT_RESP
`define macros	ALL_CAPS	MAX_DEPTH, ASSERT_ON
Instances	u_ prefix	u_fifo, u_arbiter
Generate blocks	gen_ prefix	gen_pipeline_stage
Signals (internal)	snake_case	write_enable, addr_valid

UVM Exception: UVM class member handles use m_ prefix per industry convention (m_driver, m_monitor). u_ prefix applies to RTL module instances only.

CamelCase Prohibition Examples

Forbidden (CamelCase)	Correct Form
parameter int Width = 8	parameter int unsigned WIDTH = 8
localparam AddrBits = $clog2(Depth)	localparam L_ADDR_BITS = $clog2(DEPTH)
StIdle, StProcess	ST_IDLE, ST_PROCESS
Any UpperCamelCase	ALL_CAPS or snake_case

3. Filename Conventions

Type	Pattern	Example
Module	module_name.sv	axi_lite_slave.sv
Package	module_name_pkg.sv	cabac_pkg.sv
Interface	module_name_if.sv	axi_if.sv (iverilog unsupported — do NOT generate, §4.3)
Testbench	tb_module_name.sv	tb_axi_lite_slave.sv
SVA bind	sva_module_name.sv	sva_axi_lite_slave.sv

One module per file, filename matches module name.

4. SystemVerilog Coding Rules

4.1 Mandatory Usage

• Use logic (using reg/wire is forbidden)
• always_ff for sequential (non-blocking <=)
• always_comb for combinational (blocking =)
• Actively use typedef enum / typedef struct packed
• Define shared types via packages (_pkg.sv)
• Ports: input logic / output logic (ANSI style)
• No magic numbers — use parameter or localparam

4.2 Prohibited Practices

• Using reg, wire keywords is forbidden
• Using always_latch is forbidden (except for explicit latches; generally prohibited)
• initial blocks in synthesizable code are forbidden
• Latch prevention: default is mandatory in all case statements
• Combinational loops are forbidden
• #delay in synthesizable code is forbidden
• Forward references are forbidden: all signals, types, and parameters must be declared before first use (IEEE 1800 §12.5). Xcelium (xmvlog) strictly enforces sequential declaration visibility within a module

4.3 VCS Strict always_ff Rules (Verification TB Caveat)

VCS enforces IEEE 1800 always_ff semantics strictly — a variable driven by always_ff must NOT also be driven by initial, always_comb, or task blocks (ICPD error). Verilator and iverilog are lenient on this.

RTL code: No issue — RTL should never mix always_ff with initial for the same signal.

Verification TB code (coverage counters, debug registers): If a testbench variable needs both sequential update (posedge clk) and procedural initialization (initial or task), use always @(posedge clk) instead of always_ff:

// BAD — VCS ICPD error: cov_cnt driven by always_ff AND initial
always_ff @(posedge clk) cov_cnt <= cov_cnt + 1;
initial cov_cnt = 0;

// GOOD — always @(posedge) allows multiple drivers in TB
always @(posedge clk) cov_cnt <= cov_cnt + 1;
initial cov_cnt = 0;

This applies to testbench only — synthesizable RTL must always use always_ff.

slang detection: slang -Weverything catches this same always_ff multi-driver violation at lint time (RTL mode). For TB files, use slang --allow-dup-initial-drivers to permit the initial + always_ff pattern. The run_lint.sh --tool slang wrapper auto-detects RTL vs TB based on file paths.

4.4 iverilog Incompatible Constructs (Do Not Generate)

This restriction applies to synthesizable RTL code only. Verification TBs may use interface if the target simulator supports it.

• interface / modport — unsupported by iverilog. Use port lists instead
• unpacked struct / union — unsupported by iverilog. Use individual signals or packed versions
• Agents must NOT generate these constructs in RTL code
• typedef struct packed / typedef union packed are supported (OK to use)
• Do not modify existing code or user-added code that contains these constructs

4.5 Module Structure (Mandatory Declaration Order)

IMPORTANT — IEEE 1800 §12.5 requires identifiers to be declared before first use. Xcelium (xmvlog) strictly enforces sequential declaration visibility. Reordering concurrent statements (assign, always_ff, always_comb) has zero synthesis/simulation impact, but declarations MUST always precede their first reference.

module_name_pkg.sv    <- Shared type/constant definitions
module_name.sv        <- Module implementation (order is MANDATORY):
  1. parameter declarations
  2. port declarations (ANSI style)
  3. import statements
  4. typedef / localparam / enum       <- all types and constants
  5. internal signal declarations      <- all signals before any logic
  -- declaration boundary ------------ (no declarations below this line)
  6. assign statements                 <- continuous assignments
  7. submodule instances (u_ prefix)
  8. always_comb blocks                <- combinational logic
  9. always_ff blocks                  <- sequential logic
  10. assertions (SVA)

See templates/module-template.sv for complete scaffold.

4.6 Registered Outputs (Preferred)

Prefer driving a module's outputs directly from a flip-flop. When a register/pipeline stage is needed, place the register at the output (compute → register → output port), not at the input (register input → combinational logic → output port).

// PREFERRED — registered output: the consumer gets a full clock period; the critical path stays
// inside this module; hierarchical STA and reuse are clean.
always_ff @(posedge clk or negedge rst_n) begin
  if (!rst_n) o_data <= '0;
  else        o_data <= func(a_q, b_q);   // combinational result captured into the output register
end

// DISCOURAGED — input registered, output driven through combinational logic: o_data is
// combinational AT THE PORT, so the consumer loses part of its cycle and STA must trace through
// this module's logic across the boundary.
always_ff @(posedge clk or negedge rst_n) if (!rst_n) a_q <= '0; else a_q <= i_a;
assign o_data = func(a_q);

Combinational (unregistered) outputs are acceptable for thin glue/passthrough logic, but should be a deliberate choice — not the default place to put a needed flop.

4.7 Function / Task Purity (No Hidden External Dependencies)

function/task should operate only on their arguments (pure). Avoid reading module-level signals/variables not passed in — hidden inputs cause simulation-sensitivity surprises, obscure synthesis intent, and hurt reuse/readability. Prefer passing the needed signals as arguments.

If an external (non-argument) dependency is genuinely unavoidable, document it in a header comment at the top of the function/task:

// External deps (read): cfg_mode, base_addr   <- MANDATORY when not argument-only
function automatic logic [W-1:0] map_addr(input logic [W-1:0] offset);
  map_addr = base_addr + (cfg_mode ? (offset << 1) : offset);  // reads module signals — discouraged
endfunction

5. Context-Specific Optimizations (Summary)

The items below apply only when specific optimizations are needed. See the <Advanced> section for detailed patterns and code examples.

• Power Optimization: Clock gating (ICG), operand isolation, power domains → <Advanced> section A.1
• Memory Wrapper Patterns: Storage selection, SRAM wrappers (SP/TP/DP), foundry replacement → <Advanced> section A.2
• FPGA Considerations: BRAM/DSP inference, XDC constraints, ILA debugging, IP Core → <Advanced> section A.3
• Pipelining for Timing Closure: Pipeline insertion criteria, retiming, valid/ready pipelining → <Advanced> section A.4

A.1 Power Optimization

Clock Gating

• Gate the clock for inactive blocks to reduce dynamic power
• Use of ICG (Integrated Clock Gating) cells is recommended

// Clock gating pattern
logic clk_enable;
logic gated_clk;

// Use dedicated ICG cell (synthesis tool maps to library cell)
assign gated_clk = sys_clk & clk_enable;  // For simulation only
// Synthesis: replace with ICG instantiation or let tool infer

Power-Aware Coding Patterns

• Minimize unnecessary toggling: check enable before mux output
• Memory read enable: only read SRAM when needed
• Operand isolation: mask operator inputs to zero

// Operand isolation — prevent unnecessary switching in multiplier
logic [15:0] mul_a_gated, mul_b_gated;
assign mul_a_gated = i_mul_valid ? i_mul_a : '0;
assign mul_b_gated = i_mul_valid ? i_mul_b : '0;
assign mul_result  = mul_a_gated * mul_b_gated;

Power Domain Considerations

• Explicitly specify level shifter placement for multi-voltage domains
• Mark retention registers with comments when needed

A.2 Memory Wrapper Patterns

Storage Selection by Size

Total Bits	Access Pattern	Implementation	Rationale
≤256	any	Flip-flop array (logic [W-1:0] name [0:D-1])	SRAM overhead exceeds benefit
257–4096	1 R/W	sram_sp wrapper	Area-efficient; register acceptable with rationale
257–4096	R+W simultaneous	sram_tp (single-clock) or sram_dp (dual-clock)	Separate read/write ports
>4096	any	SRAM wrapper (mandatory)	Register file wastes area and power
any	>2 ports	Flip-flop array (register file)	Multi-port SRAM macros are rare in modern processes

Standard SRAM Wrapper — Single-Port (SP)

Place in rtl/common/sram_sp.sv. One R/W port, single clock. Instance with u_mem_ prefix.

module sram_sp #(
  parameter int DEPTH = 256,
  parameter int WIDTH = 32
) (
  input  logic                    clk,
  input  logic                    i_ce,
  input  logic                    i_we,
  input  logic [$clog2(DEPTH)-1:0] i_addr,
  input  logic [WIDTH-1:0]        i_wdata,
  output logic [WIDTH-1:0]        o_rdata
);

`ifdef RAT_MEM_TSMC_N22
  // ── Compiled SRAM macro (TSMC N22) — replace with the real instance + pin map ──
  // TS1N22ULLSBLVTC256X32M4SWBASO u_macro (
  //   .CLK(clk), .CEB(~i_ce), .WEB(~i_we), .A(i_addr), .D(i_wdata), .Q(o_rdata));
`elsif RAT_MEM_SKY130
  // ── Compiled SRAM macro (SkyWater 130) ──
  // sky130_sram_1rw1r_... u_macro ( ... );
`else
  // ── Behavioral model — SIMULATION ONLY (skipped at synthesis) ──
  // synopsys translate_off
  logic [WIDTH-1:0] mem [0:DEPTH-1];
  always_ff @(posedge clk) begin
    if (i_ce) begin
      if (i_we) mem[i_addr] <= i_wdata;
      o_rdata <= mem[i_addr];  // 1-cycle read latency
    end
  end
  // synopsys translate_on
`endif

endmodule

Synthesis Behavior (translate_off blackbox + compiled macro)

The behavioral array is wrapped in // synopsys translate_off … translate_on, so DC/Genus skip it during synthesis (simulators still run it) — the 2-D array is never elaborated into flip-flops. Selecting a process define (e.g. +define+RAT_MEM_TSMC_N22, passed by run_syn.sh --mem-process) activates a compiled-macro branch instead.

run_syn.sh handles the rest automatically (DC/Genus). A real macro needs BOTH --mem-process (to activate the `ifdef branch) AND --mem-lib (to resolve its timing):

• Missing either → the wrapper is blackboxed (set_dont_touch + set_disable_timing on the instantiated memory cells, gated on get_cells) and the tool prints a WARNING. Fast synthesis, no flop array, no STA through the memory boundary.
• --mem-process <NAME> + --mem-lib <macro.db|.lib> → the macro is instantiated and the library linked for real timing/area.

Apply the same `ifdef-macro + translate_off structure to sram_tp and sram_dp. Detail: plugin_docs/specs/2026-05-26-synth-memory-blackbox-design.md.

Standard SRAM Wrapper — Two-Port (TP)

Place in rtl/common/sram_tp.sv. Separate read and write ports, single clock. Use when simultaneous read+write is needed within the same clock domain.

module sram_tp #(
  parameter int DEPTH = 256,
  parameter int WIDTH = 32
) (
  input  logic                    clk,
  // Write port
  input  logic                    i_wen,
  input  logic [$clog2(DEPTH)-1:0] i_waddr,
  input  logic [WIDTH-1:0]        i_wdata,
  // Read port
  input  logic                    i_ren,
  input  logic [$clog2(DEPTH)-1:0] i_raddr,
  output logic [WIDTH-1:0]        o_rdata
);

  // Behavioral model — SIMULATION ONLY. For synthesis, add the sram_sp `ifdef
  // compiled-macro branches above this block; the behavioral body stays translate_off-guarded.
  // synopsys translate_off
  logic [WIDTH-1:0] mem [0:DEPTH-1];

  always_ff @(posedge clk) begin
    if (i_wen) begin
      mem[i_waddr] <= i_wdata;
    end
    if (i_ren) begin
      o_rdata <= mem[i_raddr];  // 1-cycle read latency
    end
  end
  // synopsys translate_on

endmodule

Standard SRAM Wrapper — Dual-Port (DP)

Place in rtl/common/sram_dp.sv. Separate read and write ports, dual clock (wclk/rclk). Use at clock domain crossings (e.g., async FIFO memory backend, cross-domain shared buffer).

module sram_dp #(
  parameter int DEPTH = 256,
  parameter int WIDTH = 32
) (
  // Write port (write clock domain)
  input  logic                    wclk,
  input  logic                    i_wen,
  input  logic [$clog2(DEPTH)-1:0] i_waddr,
  input  logic [WIDTH-1:0]        i_wdata,
  // Read port (read clock domain)
  input  logic                    rclk,
  input  logic                    i_ren,
  input  logic [$clog2(DEPTH)-1:0] i_raddr,
  output logic [WIDTH-1:0]        o_rdata
);

  // Behavioral model — SIMULATION ONLY. For synthesis, add the sram_sp `ifdef
  // compiled-macro branches above this block; the behavioral body stays translate_off-guarded.
  // synopsys translate_off
  logic [WIDTH-1:0] mem [0:DEPTH-1];

  always_ff @(posedge wclk) begin
    if (i_wen) begin
      mem[i_waddr] <= i_wdata;
    end
  end

  always_ff @(posedge rclk) begin
    if (i_ren) begin
      o_rdata <= mem[i_raddr];  // 1-cycle read latency (rclk domain)
    end
  end
  // synopsys translate_on

endmodule

Note: sram_dp has two always_ff blocks writing different signals (mem from wclk, o_rdata from rclk), which is correct — no multi-driver conflict since each signal has a single driver.

Read Latency: Register File vs SRAM

• Register file (flip-flop array): combinational read (0-cycle) — use when downstream logic requires same-cycle data
• SRAM wrapper: synchronous read (1-cycle) — matches real SRAM macro behavior; pipeline must account for read latency

Anti-Pattern: Combinational Read on Large Storage (DO NOT)

// BAD: >4096-bit register array with combinational MUX
// Real case: 4096×13-bit line buffer → 500K+ gate equivalents,
// 5h+ DC compile, 55% area wasted, 4096:1 MUX per bit on critical path
logic signed [12:0] lb_mem [4096];
always_comb begin
  rd_data = lb_mem[rd_addr];  // 4096:1 MUX — area/timing/compile disaster
end

// GOOD: Use SRAM wrapper with synchronous read (1-cycle latency)
sram_tp #(.DEPTH(4096), .WIDTH(13)) u_mem_line_buf (
  .clk    (clk),
  .i_wen  (wr_en),  .i_waddr(wr_addr), .i_wdata(wr_data),
  .i_ren  (rd_en),  .i_raddr(rd_addr), .o_rdata(rd_data)  // 1-cycle latency
);

Foundry Macro Replacement

• Behavioral wrappers are used for simulation and FPGA synthesis (infers BRAM)
• For ASIC: replace wrapper body with foundry macro behind `ifdef SYNTHESIS guard
• Wrapper interface stays identical — no changes to instantiating modules
• DEPTH/WIDTH parameters must match foundry macro configuration

A.3 FPGA Considerations

Resource Inference Guide

Resource	Inference Pattern	Notes
BRAM	logic [W-1:0] mem [0:D-1] + sync read	Async read infers distributed RAM
DSP	a * b + c pattern	Better inference with pipeline registers
SRL	shift register (always_ff chain)	Auto-inferred, no explicit control needed

XDC Constraints (Xilinx)

• Similar to SDC but includes Xilinx-specific commands
• create_clock, set_input_delay, set_output_delay are identical
• FPGA-specific: set_property IOSTANDARD, set_property LOC

ILA Debugging

• Apply (* mark_debug = "true" *) attribute to signals targeted for debug
• Insert ILA core after synthesis for real-time waveform inspection

IP Core Usage

• Xilinx: AXI Interconnect, MIG (DDR controller), AXI DMA
• Intel: Platform Designer (Qsys) IP
• IP instances also follow the u_ prefix convention

A.4 Pipelining for Timing Closure

Pipeline Insertion Criteria

• When timing reports show critical path violations
• When combinational depth exceeds the allowable range for target frequency
• When logic depth warnings are generated by the rtl-synth-check skill

Pipeline Patterns

// Before: long combinational path
assign o_result = func_a(func_b(func_c(i_data)));

// After: 2-stage pipeline
logic [W-1:0] stage1_q;
always_ff @(posedge sys_clk or negedge sys_rst_n) begin
  if (!sys_rst_n) stage1_q <= '0;
  else            stage1_q <= func_c(i_data);
end
assign o_result = func_a(func_b(stage1_q));

Register Retiming

• Leverage the synthesis tool's retiming option (DC: compile_ultra -retime, Genus: syn_opt -retiming)
• Do not apply dont_touch to registers targeted for retiming

Valid/Ready Pipeline

• When inserting pipeline stages, pipeline the handshake signals as well
• Backpressure propagation: o_ready propagates backward from the next stage's i_ready

<Tool_Usage> This skill is not executed directly. It is referenced by agents that generate SV code (e.g., rtl-coder, sva-extractor). Agents should follow the conventions defined here. </Tool_Usage>

Follows project rules: ALL_CAPS parameter, L_ prefix localparam, snake_case, no CamelCase. ```systemverilog module cabac_encoder #( parameter int unsigned CTX_ADDR_W = 9 ) ( input logic clk, input logic rst_n, input logic [CTX_ADDR_W-1:0] ctx_addr, output logic bin_valid ); localparam int unsigned L_CTX_DEPTH = 2 ** CTX_ADDR_W;

typedef enum logic [1:0] { ST_IDLE, ST_ENCODE, ST_DONE } state_e;

</Good>
<Bad>
CamelCase, suffix, reg/wire, magic numbers:
```systemverilog
module cabac_encoder #(
  parameter int CtxAddrWidth = 9   // WRONG: CamelCase
) (
  input  wire        clk_i,        // WRONG: suffix, wire
  input  reg         rst_ni,       // WRONG: reg, suffix
  input  [8:0]       ctx_addr_i,   // WRONG: suffix, magic width
  output             bin_valid_o   // WRONG: no type, suffix
);
  localparam AddrBits = 4;         // WRONG: CamelCase, no L_ prefix
  typedef enum logic [1:0] {
    StIdle, StEncode, StDone       // WRONG: CamelCase enum values
  } state_e;

<Escalation_And_Stop_Conditions>

• Convention violation found during rtl-lint-check → request fix from rtl-coder
• Power optimization pattern affects functionality → request review from rtl-architect
• Different patterns needed for FPGA vs ASIC target → confirm target with user </Escalation_And_Stop_Conditions>

<Final_Checklist>

• Port naming: i_/o_/io_ prefix mandatory
• Clock: clk (single) or {domain}_clk (multi), Reset: rst_n or {domain}_rst_n
• No CamelCase: Parameter ALL_CAPS, localparam L_ prefix, enum values ALL_CAPS
• Use logic only (no reg/wire)
• always_ff (sequential), always_comb (combinational)
• default present in all case statements
• Instance u_ prefix, generate gen_ prefix
• No magic numbers (use parameter/localparam)
• Filename = module name
• One module per file
• Declaration order: all logic/typedef/localparam before first assign/always (no forward references)
• Storage >256 bits uses sram_sp/sram_tp/sram_dp wrapper from rtl/common/ (not inline array)
• TP (single-clock R+W) vs DP (dual-clock R+W) selected correctly per clock domain
• SRAM instances named u_mem_{purpose} </Final_Checklist>